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rev. d information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. no license is granted by implication or otherwise under any patent or patent rights of analog devices. trademarks and registered trademarks are the property of their respective companies. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781/329-4700 www.analog.com fax: 781/326-8703 ?2003, analog devices, inc. all rights reserved. ad588 * high precision voltage reference features low drift: 1.5 ppm/ c low initial error: 1 mv pin programmable output: +10 v, +5 v, +65 v tracking, ? v, ?0 v flexible output force and sense terminals high impedance ground sense machine lnsertable dip packaging mil-std-883 compliant versions available functional block diagram r3 r b r1 r2 r4 r5 r6 gain adj gnd sense +in gnd sense ?n v low bal adj v ct a4 in ? s +v s a4 out force a4 out sense a3 out force a3 out sense a3 in v high noise reduction a1 a4 ad588 a3 a2 general description the ad588 represents a major advance in the state-of-the-art in monolithic voltage references. low initial error and low tem- perature drift give the ad588 absolute accuracy performance previously not available in monolithic form. the ad588 uses a proprietary ion-implanted buried zener diode, and laser-wafer- drift trimming of high stability thin-film resistors to provide outstanding performance at low cost. the ad588 includes the basic reference cell and three additional amplifiers that provide pin programmable output ranges. the amplifiers are laser-trimmed for low offset and low drift to main- tain the accuracy of the reference. the amplifiers are configured to allow kelvin connections to the load and/or boosters for driv- ing long lines or high current loads, delivering the full accuracy of the ad588 where it is required in the application circuit. the low initial error allows the ad588 to be used as a system reference in precision measurement applications requiring 12-bit absolute accuracy. in such systems, the ad588 can provide a known voltage for system calibration in software, and the low drift allows compensation for the drift of other components in a system. manual system calibration and the cost of periodic recalibration can therefore be eliminated. furthermore, the mechanical instability of a trimming potentiometer and the potential for improper calibration can be eliminated by using the ad588 in conjunction with autocalibration software. the ad588 is available in four versions. the AD588JQ and ad588kq and grades are packaged in a 16-lead cerdip and are specified for 0 c to 70 c operation. ad588aq and bq grades are packaged in a 16-lead cerdip and are specified for the ?5 c to +85 c industrial temperature range. * protected by patent number 4,644,253. product highlights 1. the ad588 offers 12-bit absolute accuracy without any user adjustments. optional fine-trim connections are provided for applications requiring higher precision. the fine trimming does not alter the operating conditions of the zener or the buffer amplifiers, and thus does not increase the temperature drift. 2. output noise of the ad588 is very low?ypically 6 v p-p. a pin is provided for additional noise filtering using an exter- nal capacitor. 3. a precision 5 v tracking mode with kelvin output connec- tions is available with no external components. tracking error is less than 1 mv and a fine-trim is available for applications requiring exact symmetry between the +5 v and ? v out puts. 4. pin strapping capability allows configuration of a wide vari- ety of outputs: 5 v, +5 v, +10 v, ? v, and ?0 v dual outputs or +5 v, ? v, +10 v, and ?0 v single outputs.
rev. d e2e ad588especifications (typical @ 25 c, 10 v output, v s = 15 v, unless otherwise noted. 1 ) AD588JQ/aq ad588bq/kq parameter min typ max min typ max unit output voltage error +10 v, e10 v outputs 3e1 +1 mv +5 v, e5 v outputs 3e1 +1 mv 5 v tracking mode symmetry error 1.5 0.75 mv output voltage drift 0 c to 70 c (j, k, b) 2 3 1.5 ppm/ c e25 c to +85 c (a, b) 3 3 ppm/ c gain adj and bal adj 2 trim range 4 4mv input resistance 150 150 k line regulation t min to t max 3 200 200 v/v load regulation t min to t max +10 v output, 0 ma < i out < 10 ma 50 50 v/ma e10 v output, e10 ma < i out < 0 ma 50 50 v/ma supply current t min to t max 6 10 6 10 ma power dissipation 180 300 180 300 mw output noise (any output) 0.1 hz to 10 hz 6 6 v p-p spectral density, 100 hz 100 100 nv/ hz z
rev. d ad588 e3e caution esd (electrostatic discharge) sensitive device. electrostatic charges as high as 4000 v readily accumulate on the human body and test equipment and can discharge without detection. although the ad588 features proprietary esd protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality. ordering guide part number 1 initial error (mv) temperature coefficient 2 temperature range ( c) package option ad588aq 3 3 ppm/ c e25 to +85 cerdip (q-16) ad588bq 1 1.5 ppm/ c e25 to +85 2 cerdip (q-16) AD588JQ 3 3 ppm/ c0 to 70 cerdip (q-16) ad588kq 1 1.5 ppm/ c0 to 70 cerdip (q-16) notes 1 for details on grade and package offerings screened in accordance with mil-std-883, refer to the analog devices military produc ts databook or current ad588/883b. 2 temperature coefficient specified from 0 c to 70 c. absolute maximum ratings * +v s to ev s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 36 v power dissipation (25 c) . . . . . . . . . . . . . . . . . . . . . . 600 mw storage temperature range . . . . . . . . . . . . . e65 c to +150 c lead temperature range (soldering 10 sec) . . . . . . . . . 300 c package thermal resistance ( ja / jc ) . . . . . . . . 90 c/25 c/w output protection: all outputs safe if shorted to ground * stresses above those listed under absolute maximum ratings may cause perma- nent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. top view (not to scale) 16 15 14 13 12 11 10 9 1 2 3 4 5 6 7 8 a3 out force +v s a3 out sense a3 in gain adj v high noise reduction v low ev s a4 out force a4 out sense a4 in bal adj v ct gnd sense ein gnd sense +in ad588 pin configuration
rev. d e4e ad588 theory of operation the ad588 consists of a buried zener diode reference, ampli fiers used to provide pin programmable output ranges, and associ- ated thin-film resistors as shown in figure 1. the tem perature compensation circuitry provides the device with a temperature coefficient of 1.5 ppm/ c or less. r3 r b r1 r2 r4 r5 r6 gain adj gnd sense +in gnd sense ein v low bal adj v ct a4 in ev s +v s a4 out force a4 out sense a3 out force a3 out sense a3 in v high noise reduction a1 a4 ad588 a3 a2 figure 1. ad588 functional block diagram amplifier a1 performs several functions. a1 primarily acts to amplify the zener voltage from 6.5 v to the required 10 v output. in addition, a1 also provides for external adjustment of the 10 v output through pin 5, gain adj. using the bias compen- sation resistor between the zener output and the noninverting i nput to a1, a capacitor can be added at the noise reduction pin (pin 7) to form a low-pass filter and reduce the noise contri- bution of the zener to the circuit. two matched 10 k nominal thin-film resistors (r4 and r5) divide the 10 v output in half. pin v ct (pin 11) provides access to the center of the voltage span and pin 12 (bal adj) can be used for fine adjustment of this division. ground sensing for the circuit is provided by amplifier a2. the noninverting input (pin 9) senses the system ground, which will be transferred to the point on the circuit where the invert- ing input (pin 10) is connected. this may be pin 6, 8, or 11. the output of a2 drives pin 8 to the appropriate voltage. t hus, if pin 10 is connected to pin 8, the v low pin will be the same voltage as the system ground. alternatively, if pin 10 is con- nected to the v ct pin, it will be ground and pin 6 and pin 8 will be +5 v and e5 v, respectively. amplifiers a3 and a4 are internally compensated and are used to buffer the voltages at pins 6, 8, and 11, as well as to provide a full kelvin output. thus, the ad588 has a full kelvin capability by providing the means to sense a system ground and provide forced and sensed outputs referenced to that ground. applying the ad588 the ad588 can be configured to provide +10 v and e10 v reference outputs as shown in figures 2a and 2c, respectively. it can also be used to provide +5 v, e5 v, or a 5 v tracking reference, as shown in figure 2b. table i details the appropriate pin connections for each output range. in each case, pin 9 is connected to system ground and power is applied to pins 2 and 16. the architecture of the ad588 provides ground sense and un committed output buffer amplifiers that offer the user a great deal of functional flexibility. the ad588 is specified and tested in the configurations shown in figure 2a. the user may choose to take advantage of the many other configuration options avail able with the ad588. however, performance in these configurations is not guaranteed to meet the extremely stringent data sheet specifications. as indicated in table i, a +5 v buffered output can be provided using amplifier a4 in the +10 v configuration (figure 2a). a e5 v buffered output can be provided using amplifier a3 in the e10 v configuration (figure 2c). specifications are not guaranteed for the +5 v or e5 v outputs in these configurations. performance will be similar to that specified for the +10 v or e10 v outputs. as indicated in table i, unbuffered outputs are available at pins 6, 8, and 11. loading of these unbuffered outputs will impair circuit performance. amplifiers a3 and a4 can be used interchangeably. however, the ad588 is tested (and the specifications are guaranteed) with the amplifiers connected as indicated in figure 2a and table i. when either a3 or a4 is unused, its output force and sense pins should be connected and the input tied to ground. two outputs of the same voltage may be obtained by connect- ing both a3 and a4 to the appropriate unbuffered output on pins 6, 8, or 11. performance in these dual-output configura- tions will typically meet data sheet specifications. calibration generally, the ad588 will meet the requirements of a precision system without additional adjustment. initial output voltage error of 1 mv and output noise specs of 10 v p-p allow for accuracies of 12 bits to 16 bits. however, in applications where an even greater level of accuracy is required, additional calibra- tion may be called for. provision for trimming has been made through the use of the gain adj and bal adj pins (pins 5 and 12, respectively). the ad588 provides a precision 10 v span with a center tap (v ct ) that is used with the buffer and ground sense amplifiers to achieve the voltage output configurations in table i. gain adjust and balance adjust can be used in any of these configurations to trim the magnitude of the span voltage and the position of the center tap within the span. the gain adjust should be performed first. although the trims are not interactive within the device, the gain trim will move the balance trim point as it changes the magnitude of the span.
rev. d ad588 e5e figure 2b shows gain and balance trims in a +5 v and e5 v tracking configuration. a 100 k 20-turn potentiometer is used for each trim. the potentiometer for gain trim is con- nected between pin 6 (v high ) and pin 8 (v low ) with the wiper connected to pin 5 (gain adj). the potentiometer is adjusted to produce exactly 10 v between pin 1 and pin 15, the amplifier outputs. the balance potentiometer, also connected between pin 6 and pin 8 with the wiper to pin 12 (bal adj), is then adjusted to center the span from +5 v to e5 v. trimming in other configurations works in exactly the same manner. when producing +10 v and +5 v, gain adj is used to trim +10 v and bal adj is used to trim +5 v. in the e10 v and e5 v configuration, gain adj is again used to trim the magnitude of the span, e10 v, while bal adj is used to trim the center tap, e5 v. in single output configurations, gain adj is used to trim outputs utilizing the full span (+10 v or e10 v), while bal adj is used to trim outputs using half the span (+5 v or e5 v). input impedance on both the gain adj and bal adj pins is approximately 150 k . t he gai n adj us t trim network effectively attenuates the 10 v across the trim potentiometer by a factor of about 1500 to provide a trim range of e3.5 mv to +7.5 mv with a resolution of approximately 550 v/turn (20-turn potentiometer). the bal adj trim network attenu- ates the trim voltage by a factor of about 1400, providing a trim range of 4.5 mv with resolution of 450 v/turn. r3 r b r1 r2 r4 r5 r6 ev s +v s a1 a4 ad588 a3 a2 system ground +10v +15v +5v e15v system ground 0.1 f 0.1 f figure 2a. +10 v output r3 r b r1 r2 r4 r5 r6 ev s +v s a1 a4 ad588 a3 a2 system ground +5v e15v e5v e15v system ground 0.1 f 0.1 f 100k 20t balance adjust 100k 20t gain adjust +15v noise reduction 1 f figure 2b. +5 v and e5 v outputs table i. pin connections connect buffered pin 10 unbuffered * output on pins output buffered output on pins range to pin: e10 v e5 v 0 v +5 v +10 v connections e10 v e5 v 0 v +5 v +10 v +10 v 8 8 11 6 11 to 13, 14 to 15 15 6 to 4, and 3 to 1 1 e5 v or +5 v 11 8 11 6 8 to 13, 14 to 15, 15 6 to 4, and 3 to 1 1 e10 v 6 8 11 6 8 to 13, 14 to 15, 15 11 to 4, and 3 to 1 1 +5 v 11 6 6 to 4 and 3 to 1 1 e5 v1 18 8 to 13 and 14 to 15 15 * unbuffered outputs should not be loaded.
rev. d e6e ad588 r3 r b r1 r2 r4 r5 r6 ev s +v s a1 a4 ad588 a3 a2 system ground +15v e10v e15v system ground 0.1 f 0.1 f noise reduction e5v 0.1 f 0.1 f figure 2c. e10 v output trimming the ad588 introduces no additional errors over temperature, so precision potentiometers are not required. for single-output voltage ranges, or in cases when balance adjust is not required, pin 12 should be connected to pin 11. if gain adjust is not required, pin 5 should be left floating. noise performance and reduction the noise generated by the ad588 is typically less than 6 v p-p over the 0.1 hz to 10 hz band. noise in a 1 mhz bandwidth is approximately 600 v p-p. the dominant source of this noise is the buried zener, which contributes approximately 100 nv/ hz hzhz hzhzhzhz hz hz hz z z
rev. d ad588 e7e additional load to the internal zener diode?s current source, resulting in a somewhat longer turn-on time. in the case of a 1 f capacitor, the initial turn-on time is approximately 60 ms (see figure 6). note: if the noise reduction feature is used in the 5 v configuration, a 39 k resistor between pin 6 and pin 2 is requ ired for proper startup. figure 6. turn-on with c n = 1 f temperature performance the ad588 is designed for precision reference applications where temperature performance is critical. extensive tempera- ture testing ensures that the device?s high level of performance is maintained over the operating temperature range. figure 7 shows typical output voltage drift for the ad588bd and illustrates the test methodology. the box in figure 7 is bounded on the sides by the operating temperature extremes and on top and bottom by the maximum and minimum output voltages measured over the operating temperature range. the slope of the diagonal drawn from the lower left corner of the box determines the performance grade of the device. output volts 10.002 v max v min 10.000 e35 e15 5 25 45 65 t min t max temperature e c 85 10.001 figure 7. typical ad588bd temperature drift each ad588a and b grade unit is tested at e25 c, 0 c, +25 c, +50 c, +70 c, and +85 c. this approach ensures that the variations of output voltage that occur as the temperature changes within the specified range will be contained within a box whose diagonal has a slope equal to the maximum specified drift. the position of the box on the vertical scale will change from device to device as initial error and the shape of the curve vary. maxi- mum height of the box for the appropriate temperature range is shown in figure 8. duplication of these results requires a combi- nation of high accuracy and stable temperature control in a test system. evaluation of the ad588 will produce a curve similar to that in figure 7, but output readings may vary depending on the test methods and equipment utilized. 2.10 1.05 1.40(typ) 1.05 3.30 10.80 7.20 a d588jq a d588jq a d588jq a d588jq a d588jq a d588jq 3.30 device grade maximum output change e mv 0 c to +70 c e25 c to +85 c e55 c to +125 c figure 8. maximum output change?mv kelvin connections force and sense connections, also referred to as kelvin connec- t ions, offer a convenient method of eliminating the effects of voltage drops in circuit wires. as seen in figure 9, the load current and wire resistance produce an error (v error = r i l ) at the load. the kelvin connection of figure 9 overcomes the problem by including the wire resistance within the forcing loop of the amplifier and sensing the load voltage. the amplifier corrects for any errors in the load voltage. in the circuit shown, the output of the amplifier would actually be at 10 v + v error and the voltage at the load would be the desired 10 v. the ad588 has three amplifiers that can be used to implement kelvin connections. amplifier a2 is dedicated to the ground force-sense function, while uncommitted amplifiers a3 and a4 are free for other force-sense chores. e + 10v r i l v = 10v e ri l r load r r i l r load v = 10v + ri l v = 10v i = 0 i = 0 figure 9. advantage of kelvin connection in some single-output applications, one amplifier may be unu sed. in such cases, the unused amplifier should be connected as a unity-gain follower (force + sense pin tied together), and the input should be connected to ground. an unused amplifier section may be used for other circuit functions as well. figures 10 through 14 show the typical performance of a3 and a4. frequency e hz 100 e20 10 10m 100 open-loop gain e db 1k 10k 100k 1m 80 60 40 20 0 gain phase 0 e180 e30 e60 e90 e120 e150 phase e degrees figure 10. open-loop frequency response (a3, a4) slope t.c. = vev (t e t ) 10 1 max min max min e6 = 10.0013v 10.00025v ( 85 c e25 c ) 10 10 e6 ? ? = 0.95ppm / c
rev. d e8e ad588 frequency e hz 110 10 10 10m 100 power supply rejection e db 1k 10k 100k 1m 100 80 60 40 20 v s = 15v with 1v p-p sine wave +supply esupply figure 11. power supply rejection vs. frequency (a3, a4) figure 12a. unity-gain follower pulse response (large signal) figure 12b. unity-gain follower pulse response (small signal) frequency e hz 110 0 10 10m 100 cmrr e db 1k 10k 100k 1m 100 80 60 40 20 v s = 15v v cm = 1v p-p +25 c figure 13. common-mode rejection vs. frequency (a3, a4) frequency e hz 1 10k 10 noise spectral density e nv/ hz 8 sd damcerrmace aa ad88 madda ad88 aa ara l l lc
rev. d ad588 e9e figure 15b. large-scale transient response figures 16a and 16b display the output amplifier characteristics driving a 5 ma to 10 ma load, a common situation found when the reference is shared among multiple converters or is used to provide a bipolar offset current. 10v a3 or a4 v out i l 10v 0v v l + e 2k 2k figure 16a. transient and constant load test circuit figure 16b. transient response 5 ma to10 ma load in some applications, a varying load may be both resistive and capacitive in nature or be connected to the ad588 by a long capacitive cable. figures 17a and 17b display the output amplifier characteristics driving a 1,000 pf, 0 ma to 10 ma load. 10v a3 or a4 v out 10v 0v v l 1k 1000pf c l figure 17a. capacitive load transient response test circuit figure 17b. output response with capacitive load figures 18a and 18b display the crosstalk between output am- plifiers. the top trace shows the output of a4, dc-coupled and offset by 10 v, while the output of a3 is subjected to a 0 ma to 10 ma load current step. the transient at a4 settles in about 1 s, and the load-induced offset is about 100 v. 10v 0v v l 1k 10v v out 10v a4 a3 + e + e figure 18a. load crosstalk test circuit figure 18b. load crosstalk
rev. d e10e ad588 attempts to drive a large capacitive load (in excess of 1,000 pf) may result in ringing or oscillation, as shown in the step re sponse photo (figure 19a). this is due to the additional pole formed by the load capacitance and the output impedance of the amplifier, which consumes phase margin. the recommended method of driving capacitive loads of this magnitude is shown in figure 19b. the 150 resistor isolates the capacitive load from the output stage, while the 10 k resistor provides a dc feedback path and preserves the output accuracy. the 1 f capacitor provides a high frequency feedback loop. the performance of this circuit is shown in figure 19c. figure 19a. output amplifier step response, c l = 1 f v in v out + e 10k 1 f c l 1 f 150 figure 19b. compensation for capacitive loads figure 19c. output amplifier step response using figure 19b compensation using the ad588 with converters the ad588 is an ideal reference for a wide variety of a/d and d/a converters. several representative examples follow. 14-bit digital-to-analog converter?ad7535 high resolution cmos d/a converters require a reference voltage of high precision to maintain rated accuracy. the combination of the ad588 and ad7535 takes advantage of the initial accu- racy, drift, and full kelvin output capability of the ad588 as well as the resolution, monotonicity, and accuracy of the ad7535 to produce a subsystem with outstanding characteristics. see figure 20. 16-bit digital-to-analog converter?ad569 another application that fully utilizes the capabilities of the ad588 is supplying a reference for the ad569, as shown in figure 21. amplifier a2 senses system common and forces v ct to assume this value, producing +5 v and e5 v at pin 6 and pin 8, respectively. amplifiers a3 and a4 buffer these voltages out to the appropriate reference force-sense pins of the ad569. the full kelvin scheme eliminates the effect of the circuit traces or wires and the wire bonds of the ad588 and ad569 them- selves, which would otherwise degrade system performance. substituting for internal references many converters include built-in references. unfortunately, such references are the major source of drift in these converters. by using a more stable external reference like the ad588, drift performance can be improved dramatically.
rev. d ad588 e11e r3 r b r1 r2 r4 r5 r6 ev s +v s a1 a4 ad588 a3 a2 14-bit dac ls input register ms input register dac register v refs v reff agnds agndf +10v n.c. v dd r fs i out ldac cslsb csms b wr ss dd db db 8 ad ad88adc a a a a ad88 a a a a a a a a l c h re rce re sese a s e l e c r re sese re rce 8msb 8lsb d cs ldac db db hbe lbe s s s e m e s e l e c r laches ad ha rad
rev. d e12e ad588 12-bit analog-to-digital converter?ad574a the ad574a is specified for gain drift from 10 ppm/ c to 50 ppm/ c, (depending on grade) using its on-chip reference. the reference contributes typically 75% of this drift. therefore, the total drift using an ad588 to supply the reference can be improved by a factor of 3 to 4. using this combination may result in apparent increases in full- scale error due to the difference between the on-board reference by which the device is laser-trimmed and the external reference with which the device is actually applied. the on-board refer ence is specified to be 10 v 100 mv, while the external reference is specified to be 10 v 1 mv. this may result in up to 101 mv of apparent full-scale error beyond the 25 mv specified ad574 gain error. external resistors r2 and r3 allow this error to be nulled. t heir contribution to full-scale drift is negligible. the high output drive capability allows the ad588 to drive up to six converters in a multiconverter system. all converters will have gain errors that track to better than 5 ppm/ c. rtd excitation the resistance temperature detector (rtd) is a circuit element whose resistance is characterized by a positive temperature coefficient. a measurement of resistance indicates the measured temperature. unfortunately, the resistance of the wires leading to the rtd often adds error to this measurement. the 4-wire ohms measurement overcomes this problem. this method uses two wires to bring an excitation current to the rtd and two additional wires to tap off the resulting rtd voltage. if these additional two wires go to a high input impedance measurement circuit, the effect of their resistance is negligible. therefore, they transmit the true rtd voltage. i exc r r i = 0 rtd v out r rtd + e i = 0 r r figure 23. 4-wire ohms measurement a practical consideration when using the 4-wire ohms technique with an rtd is the self-heating effect that the excitation current has on the temperature of the rtd. the designer must choose the smallest practical excitation current that still gives the de sired resolution. rtd manufacturers usually specify the self-heating effect of each of their models or types of rtds. figure 24 shows an ad588 providing the precision excitation current for a 100 rtd. the small excitation current of 1 ma dissipates a mere 0.1 mw of power in the rtd. r3 r b r1 r2 r4 r5 r6 a1 a4 ad588 a3 a2 12 8 cs a r c ce re re b aacm ss hh bs mddle bs lw bs d cm ada s s r r r r ad88adac
rev. d ad588 e13e r3 r b r1 r2 r4 r5 r6 ev s +v s a1 ad588 a3 a2 100 1.0ma 0.01% + e v out r c = 10k r c vishay s102c or similar rtd = omega k4515 0.24 c/mw self-heating e15v or ground a4 figure 24. precision current source for rtd boosted precision current source in the rtd current-source application, the load current is limited to 10 ma by the output drive capability of amplifier a3. in the event that more drive current is needed, a series-pass transistor can be inserted inside the feedback loop to provide higher current. accuracy and drift performance are unaffected by the pass transistor. r3 r b r1 r2 r4 r5 r6 ev s +v s a1 a4 ad588 a3 a2 load v cc q 1 i l = 10v r c 220 limited by q 1 and r c power dissipation figure 25. boosted precision current source bridge driver circuits the wheatstone bridge is a common transducer. in its simplest f orm, a bridge consists of four, two-terminal elements con nected to form a quadrilateral, a source of excitation connected along one of the diagonals and a detector comprising the other diago- nal. figure 26a shows a simple bridge driven from a unipolar excitation supply. eo, a differential voltage, is proportional to the deviation of the element from the initial bridge values. un for- tunately, this bridge output voltage is riding on a comm on-mode voltage equal to approximately v in /2. further processing of this signal may necessarily be limited to high common-mode rejec- tion techniques such as instrumentation or isolation amplifiers. figure 26b shows the same bridge transducer, this time driven from a pair of bipolar supplies. this configuration ideally elimi- nates the common-mode voltage and relaxes the restrictions on any processing elements that follow. v in e + r4 r3 r2 r1 e o + e figure 26a. bridge transducer excitation? unipolar drive v 1 r4 r3 r2 r1 e o + e v 2 e + e + figure 26b. bridge transducer excitation? bipolar drive r3 r b r1 r2 r4 r5 r6 ev s +v s a1 a4 ad588 a3 a2 q 1 = 2n3904 220 +15v e15v 220 q 2 = 2n3904 e o + e figure 27. bipolar bridge drive as shown in figure 27, the ad588 is an excellent choice for the control element in a bipolar bridge driver scheme. transistors q1 and q2 serve as series-pass elements to boost the current drive capability to the 28 ma required by a typical 350 bridge. a differential gain stage may still be required if the bridge balance is not perfect. such gain stages can be expensive.
rev. d e14e ad588 figure 28. floating bipolar bridge drive with minimum cmv r3 r b r1 r2 r4 r5 r6 ev s +v s a1 a4 ad588 a3 a2 r1 r2 ad op-07 v out + e q 1 = 2n3904 220 +15v e15v 220 q 2 = 2n3904 additional common-mode voltage reduction is realized by using the circuit illustrated in figure 28. a1, the ground sense ampli- fier, serves the supplies on the bridge to maintain a virtual ground at one center tap. the voltage that appears on the opposite center tap is now single-ended (referenced to ground) and can be amplified by a less expensive circuit.
rev. d ad588 ?5 outline dimensions 16-lead ceramic dip-glass hermetic seal package [cerdip] (q-16) dimensions shown in inches and (millimeters) 16 18 9 0.310 (7.87) 0.220 (5.59) pin 1 0.005 (0.13) min 0.098 (2.49) max 15 0 0.320 (8.13) 0.290 (7.37) 0.015 (0.38) 0.008 (0.20) seating plane 0.200 (5.08) max 0.840 (21.34) max 0.150 (3.81) min 0.200 (5.08) 0.125 (3.18) 0.023 (0.58) 0.014 (0.36) 0.100 (2.54) bsc 0.070 (1.78) 0.030 (0.76) 0.060 (1.52) 0.015 (0.38) controlling dimensions are in inches; millimeters dimensions (in parentheses) are rounded-off inch equivalents for reference only and are not appropriate for use in design revision history location page 2/03?ata sheet changed from rev. c to rev. d. added kq model and deleted sq and tq models . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . universal changes to general description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 change to product highlights . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 changes to specifications . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 change to ordering guide . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 updated outline dimensions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 10/02?ata sheet changed from rev. b to rev. c. changes to general description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 changes to specifications . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 changes to ordering guide . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 changes to table 1 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 deleted figure 10c . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 outline dimensions updated . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
c00531?2/03(d) printed in u.s.a. ?6

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